Method for Tracking a Transmitter by Means of a Synthetic Sparse Antenna Network

ABSTRACT

Method of locating one or more transmitters on the basis of an array of sensors moving with respect to the transmitters comprising at least the following steps: 
         determining the direction vectors â k  corresponding to the response of the array of sensors to a source with incidence (θ, Δ) as a function of the incidence parameters θ, Δ, and of the parameter p related to the distortion of the phases on the sensors,    transforming this vector â k  so as to eliminate the unknown parameter p, into a vector Ĉ km , Ĉ′ km , using the transformed vector to obtain the position of the transmitter using a maximized locating criterion.

The invention relates to a method of locating one or more transmitters stationary or mobile on the ground on the basis of the running of a carrier and of an onboard sensor producing the associated direction vectors.

It is applied for example with an array of synthetic sparse antennas.

The prior art describes various procedures for locating one or more transmitters on the basis of running carriers.

FIG. 1 illustrates an example of airborne locating. The transmitter 1 to be located is at the position (x₀,y₀,z₀); the carrier 2 at the instant t_(k) is at the position (x_(k),y_(k),z_(k)) and sees the transmitter at the incidence (θ(t_(k),x₀,y₀,z₀), Δ(t_(k),x₀,y₀,z₀) ). The angles θ(t,x₀,y₀,z₀) and Δ(t,x₀,y₀,z₀) evolve over time and depend on the position of the transmitter as well as the trajectory of the carrier. The angles θ(t,x₀,y₀,z₀) and Δ(t,x₀,y₀,z₀) are for example labeled as shown by FIG. 2 with respect to an array of N antennas that may be fixed under the carrier.

There currently exist several families of locating techniques making it possible to determine the position (x_(m),y_(m),z_(m)) of a transmitter on the basis of the direction vectors. These locating techniques differ through the geometric constraints or characteristics of the antennal array; they are classed into several categories cited hereafter.

Use of Unambiguous, Paired, Standardized And Calibrated Arrays And of Goniometry Techniques

These techniques are in most cases based on 1D azimuthal goniometry. The azimuths θ_(km)=θ(t_(k),x_(m),y_(m),z_(m)) associated with the m^(th) transmitter are measured for various instants t_(k). By using the position (x_(k),y_(k),z_(k)) of the carrier at this instant k, a position (x_(mk),y_(mk),z_(mk)) of this transmitter is estimated through a ground intersection. The position (x_(k),y_(k),z_(k)) of the carrier is given by a GPS. Its orientation is given by a compass in the case of a terrestrial carrier, and by a navigation platform in the case of an aircraft. On the basis of all the positions (x_(mk),y_(mk),z_(mk)) an extraction of data is performed making it possible to determine the dominant position (x_(m),y_(m),z_(m)) of the incident transmitter. Locating is done by triangulation or by ground intersection (2D goniometry). The drawback of triangulation techniques is that they require a significant transit. Moreover, in antennal constraint terms, these goniometry techniques must use an unambiguous array of sensors, and require calibration, pairing and standardization of the channels.

Use of Sparse Array of Paired Antennas

The applicant's patent application FR 03/13128 describes a method which makes it possible to effect direct estimation of the position (x_(m),y_(m),z_(m)) of the transmitter on the basis of a multichannel parametric analysis of the direction vectors at various instants t_(k) over a duration Δt. This method requires a pairing of the channels as well as a correction of the distortions in phase and in amplitude of the receivers.

The present invention relies on a different approach which does not require, during normal operation, correction of the distortions of the receivers provided that the receiver exhibits a substantially constant response over the locating durations considered.

The invention relates to a method of locating one or more transmitters on the basis of an array of sensors moving with respect to the transmitters characterized in that it comprises at least the following steps:

-   -   determining the direction vectors â_(k) corresponding to the         response of the array of sensors to a source with incidence (θ,         Δ) as a function of the incidence parameters θ, Δ, and of the         parameter ρ related to the distortion of the phases on the         sensors,     -   transforming this vector â_(k) so as to eliminate the unknown         parameter ρ, into a transformed vector ĉ_(km), ĉ′_(km)     -   using the transformed vector to obtain the position of the         transmitter using a maximized locating criterion.

The method according to the invention exhibits the following advantages in particular:

-   -   It allows direct estimation of the positions of each of the         transmitters on the basis of a multichannel parametric analysis         at various instants t,     -   It makes it possible to use of arrays sparse sensor that are         unpaired, or even uncalibrated (large-aperture array),     -   It makes it possible to circumvent the pairing as well as the         calibration in amplitude and in phase of the reception channels,     -   It is possible to take into account a model on the variation in         the signal reception level,     -   it makes it possible to introduce any observation model deduced         from the direction vectors at different observation instants,     -   it is possible according to a variant to consider the whole set         of channels, without taking a particular reference channel.

Other characteristics and advantages of the invention will be better apparent on reading the description which follows of an example given by way of wholly nonlimiting illustration with appended figures which represent:

FIG. 1 an exemplary locating of a transmitter by an airplane equipped with an array of suitable sensors,

FIG. 2 an array of 5 antennas and the angles of incidence of a transmitter.

In order to better understand the principle implemented in the present invention, the example which follows is given by way of wholly nonlimiting illustration for a system such as shown diagrammatically in FIG. 1, comprising an airplane 2 equipped with an array of N sensors and with a processor adapted for executing the steps of the method according to the invention and with a transmitter 1 on the ground to be located.

In the presence of M transmitters, the airplane receives at the instant t at the output of the N sensors of the array, the vector x(t). Around the instant t_(k), the vector x(t+t_(k)) of dimension N×1 is the mixture of the signals of the M transmitters: $\begin{matrix} \begin{matrix} {{x\left( {t + t_{k}} \right)} = \begin{bmatrix} {x_{1}\left( {t + t_{k}} \right)} \\ M \\ {x_{N}\left( {t + t_{k}} \right)} \end{bmatrix}} \\ {= {{\sum\limits_{m = 1}^{M}{{a\left( {\theta_{k\quad m},\Delta_{k\quad m},\rho} \right)}{s_{m}\left( {t + t_{k}} \right)}}} + {b\left( {t + t_{k}} \right)}}} \\ {= {{{A_{k}(\rho)}{s\left( {t + t_{k}} \right)}} + {b\left( {t + t_{k}} \right)}}} \end{matrix} & (1) \end{matrix}$ for |t|<Δt/2

-   -   where b(t) is the noise vector assumed Gaussian,     -   a(θ, Δ, ρ) is the response of the array of sensors to a source         with incidence (θ,Δ) with complex receiver gains,     -   ρ is a parameter representative of the phase distortion on the         various reception channels, ρ=[ρ₁ . . . ρ_(N)N]^(T),     -   A_(κπ)[α(θ_(κ1), Δ_(κ1),ρ) . . . ,α(θ_(κM), Δ_(κM),ρ)],         σ(τ)=[σ₁(τ) . . . σ_(M)(τ)]^(T),         θ_(κμ)=θ(τ_(κ),ξ_(μ),ψ_(μ),ζ_(μ)) and         Δ_(km)=Δ(t_(k),x_(m),y_(m),z_(m)) and x_(n)(t) is the received         signal on the n^(th) sensor.         We note that in this model, the mixture matrix Δ_(kρ) depends on         the instant t_(k) of observation as well as on the gains of the         receivers ρ.         The direction vector a(θ,Δ,ρ) and the direction vector without         phase distortion v(θ, Δ) respectively have expressions:         $\begin{matrix}         {{a\quad\left( {\theta,\Delta\quad,\rho} \right)} = {{\begin{bmatrix}         {\rho_{1}{a_{1}\left( {\theta,\Delta} \right)}} \\         M \\         {\rho_{N}{a_{N}\left( {\theta,\Delta} \right)}}         \end{bmatrix}\quad{and}\quad{v\left( {\theta,\Delta} \right)}} = \begin{bmatrix}         {a_{1}\left( {\theta,\Delta} \right)} \\         M \\         {a_{N}\left( {\theta,\Delta} \right)}         \end{bmatrix}}} & (2)         \end{matrix}$         Where:     -   b_(n)(t) is the noise vector of channel n,     -   (θ, Δ, ρ) is the response of the array of sensors to a source         with incidence (θ,Δ),     -   v(θ, Δ) is direction vector without distortion for a source with         incidence (θ,Δ)     -   A_(k)(ρ)=[a(θ_(k1), Δ_(k1), ρ) . . . a(θ_(kM), Δ_(kM), ρ)],     -   θ_(k)=θ(t_(k),x_(m),y_(m),z_(m)) and         Δ_(k)=Δ(t_(k),x_(m),y_(m),z_(m)).

These vectors a(θ_(km), Δ_(km), ρ) have the feature of depending on the instant t_(k) and on the position (x_(m),y_(m),z_(m)) of the transmitter.

Direction Vector akm

In the presence of model errors, for example coupling, the measured direction vector â_(km)(ρ) can be written: â _(km)(ρ)=a(θ(t _(k) ,x _(m) ,y _(m) ,z _(m)), Δ(t _(k) ,x _(m) ,y _(m) ,z _(m)), ρ)+e _(km) with   (3) e_(km): complex measurement noise dependent on the calibration errors such as coupling.

In particular for an array composed of N=2 sensors spaced apart by a distance of d along the axis of the carrier the direction vector without distortion v_(km) at the instant k satisfies: $\begin{matrix} \begin{matrix} {v_{k\quad m} = \begin{bmatrix} 1 \\ {\exp\begin{pmatrix} {j\quad 2\quad\pi\quad\frac{d}{\lambda}{\cos\left( {\theta\left( {t_{k},x_{m},y_{m},z_{m}} \right)} \right)}} \\ {\cos\left( {\Delta\left( {t_{k},x_{m},y_{m},z_{m}} \right)} \right)} \end{pmatrix}} \end{bmatrix}} \\ {= {v\left( {t_{k},x_{m},y_{m},z_{m}} \right)}} \end{matrix} & (4) \end{matrix}$ The incidence (θ(t_(k),x_(m),y_(m),z_(m)), Δ(t_(k),x_(m),y_(m),z_(m))) can be calculated directly on the basis of the position (x_(m),y_(m),z_(m)) of the carrier at the instant t_(k) and of the position (x_(m),y_(m),z_(m)) of the transmitter.

The basic idea of the method relies notably on the fact that the parameter p is independent of the incidence (θ, Δ) of the sources, the vector p not being estimated by standardization or by any other procedure before or during normal operation of the system.

First Variant of Implementation of the Method Using Vectors c_(km)

According to a first variant embodiment, the method uses the following direction vector: â _(km)(ρ)=a(θ _(k), Δ_(k), ρ)+e_(km)   (5)

It constructs the vector {circumflex over (b)}_(km) of dimension (N−1)*1 by choosing a reference sensor, for example the sensor of index 1. ${\hat{b}}_{k\quad m} = \begin{bmatrix} {{{\hat{a}}_{k\quad m}(2)}/{{\hat{a}}_{k\quad m}(1)}} \\ M \\ {{{\hat{a}}_{k\quad m}(n)}/{{\hat{a}}_{k\quad m}(1)}} \\ M \\ {{{\hat{a}}_{k\quad m}(N)}/{{\hat{a}}_{k\quad m}(1)}} \end{bmatrix}$ where â_(km)(n) is the n component of â_(km) The vector {circumflex over (b)}_(km) is a function of ρ and is expressed in the following manner: $\begin{matrix} {{{\hat{b}}_{k\quad m} = {{b\left( {t_{k},x_{m},y_{m},z_{m},\rho} \right)} + w_{k\quad m}}}{where}\text{}{{b\left( {t_{k},x_{m},y_{m},z_{m},\rho} \right)} = \begin{bmatrix} {\left( {\rho_{2}\quad{v_{2}\left( {\theta_{k},\Delta_{k}} \right)}} \right)/\left( {\rho_{1}\quad{v_{1}\left( {\theta_{k},\Delta_{k}} \right)}} \right)} \\ M \\ {\left( {\rho_{N}\quad v_{N}\quad\left( {\theta_{k},\Delta_{k}} \right)} \right)/\left( {\rho_{1}\quad v_{1}\quad\left( {\theta_{k},\Delta_{k}} \right)} \right)} \end{bmatrix}}} & (6) \end{matrix}$

The vector {circumflex over (b)}_(km) is constructed on the basis of the components of the vector â_(km)(ρ). We choose for this purpose a reference channel and we construct the components of the vector as being the ratio of the components of the vector â_(km) and a reference channel which is associated for example with the 1^(st) component of â_(km). Equation (6) corresponds to the choice of sensor 1 as reference sensor.

The vector {circumflex over (b)}_(km) is thereafter transformed so as to eliminate the components of the complex vector ρ_(n). For this purpose, the method constructs the vector ĉ_(km) of dimension (N−1)×1 by choosing a reference instant, for example k=i: $\begin{matrix} {{\hat{c}}_{k\quad m} = \begin{bmatrix} {{{\hat{b}}_{k\quad m}(1)}/{{\hat{b}}_{i\quad m}(1)}} \\ M \\ {{{\hat{b}}_{k\quad m}(n)}/{{\hat{b}}_{i\quad m}(n)}} \\ M \\ {{{\hat{b}}_{k\quad m}\left( {N - 1} \right)}/{{\hat{b}}_{i\quad m}\left( {N - 1} \right)}} \end{bmatrix}} & (7) \end{matrix}$ Thus in a low noise context ||w_(km)||<<1, Ĉ_(km)(n) has the following expression: ${{\hat{c}}_{k\quad m}(n)} \approx {\frac{{\overset{\sim}{v}}_{n}\left( {\theta_{k},\Delta_{k},\rho} \right)}{{\overset{\sim}{v}}_{n}\left( {\theta_{i},\Delta_{i},\rho} \right)} + {{\overset{\sim}{w}}_{k}(n)}}$ where the non calibrated disturbed vector $\begin{matrix} {{{{\overset{\sim}{v}}_{n}\left( {\theta,\Delta,\rho} \right)} = {\frac{\rho_{n + 1}}{\rho_{1}}\frac{v_{n + 1}\left( {\theta_{k},\Delta_{k}} \right)}{v_{1}\left( {\theta_{k},\Delta_{k}} \right)}}}{{{with}\text{:}\quad{{\overset{\sim}{w}}_{k\quad m}(n)}} = \frac{{{{\overset{\sim}{v}}_{n}\left( {\theta_{i},\Delta_{i}} \right)}{w_{k\quad m}(n)}} - {{{\overset{\sim}{v}}_{n}\left( {\theta_{k},\Delta_{k}} \right)}{w_{i\quad m}(n)}}}{\left( {{\overset{\sim}{v}}_{n}\left( {\theta_{i},\Delta_{i}} \right)} \right)^{2}}}} & \left. 8 \right) \end{matrix}$ We note that the ratio {tilde over (v)}_(n)(θ_(k), Δ_(k),ρ)/{tilde over (v)}_(n)(θ_(i), Δ_(i), ρ) is independent of ρ and equals: $\begin{matrix} {{G_{n}\left( {\theta_{k},{\Delta_{k}\theta_{i}},\Delta_{i}} \right)} = {\frac{{\overset{\sim}{v}}_{n}\left( {\theta_{k},\Delta_{k},\rho} \right)}{{\overset{\sim}{v}}_{n}\left( {\theta_{i},\Delta_{i},\rho} \right)} = {\frac{v_{n + 1}\left( {\theta_{k},\Delta_{k}} \right)}{v_{1}\left( {\theta_{k},\Delta_{k}} \right)}\frac{v_{1}\left( {\theta_{i},\Delta_{i}} \right)}{v_{n + 1}\left( {\theta_{i},\Delta_{i}} \right)}}}} & (9) \end{matrix}$ Under these conditions the vector ĉ_(km) may be written in the following manner: $\begin{matrix} {{{\hat{c}}_{k\quad m} = {{c\left( {t_{k},x_{m},y_{m},z_{m}} \right)} + {\overset{\sim}{w}}_{k\quad m}}}{{{where}\quad{c\left( {t_{k},x_{m},y_{m},z_{m}} \right)}} = \begin{bmatrix} {G_{1}\left( {\theta_{k},\Delta_{k},\theta_{i},\Delta_{i}} \right)} \\ M \\ {G_{N - 1}\left( {\theta_{k},\Delta_{k},\theta_{i},\Delta_{i}} \right)} \end{bmatrix}}{{and}\quad{{\overset{\sim}{w}}_{k\quad m}(n)}\quad{is}\quad{the}\quad n^{th}\quad{component}\quad{of}\quad{\overset{\sim}{w}}_{k\quad m}}} & (10) \end{matrix}$

Locating the Transmitter

The method having determined the vector ĉ_(km), it uses it to locate the transmitters, that is to say to obtain the position (x_(m),y_(m),z_(m)) of the transmitter. For this purpose the method maximizes the normalized vector correlation criterion L_(K)(x,y,z) given by expression (11) in the position space (x,y,z) of a transmitter. $\begin{matrix} {{{L_{K}\left( {x,y,z} \right)} = \frac{{{c_{K}^{H}{v_{K,c}\left( {x,y,z} \right)}}}^{2}}{\left( {c_{K}^{H}c_{K}} \right)\left( {{v_{K,c}\left( {x,y,z} \right)}^{H}{v_{K,c}\left( {x,y,z} \right)}} \right)}}\begin{matrix} {{{with}\quad c_{K}} = \begin{bmatrix} c_{1\quad m} \\ M \\ c_{K\quad m} \end{bmatrix}} \\ {{= {{v_{K,c}\left( {x_{m},y_{m},z_{m}} \right)} + w_{K}}},{v_{K,c}\left( {x,y,z} \right)}} \\ {= \begin{bmatrix} {c\left( {t_{1},x,y,z} \right)} \\ M \\ {c\left( {t_{K},x,y,z} \right)} \end{bmatrix}} \end{matrix}{{{and}\quad w_{K}} = \begin{bmatrix} {\overset{\sim}{w}}_{1\quad m} \\ M \\ {\overset{\sim}{w}}_{K\quad m} \end{bmatrix}}} & (11) \end{matrix}$

In order to refine the estimation of the position (x_(m),y_(m),z_(m)) of the transmitters, the method can be implemented in an iterative manner. For this purpose, the method executes together for example the following steps:

-   -   Step I1 Identification of the vectors C(_(K+1)m) at the instant         t_(k+1).     -   Step I2 Calculation of the criterion L_(K+1)(x,y,z) in an         iterative manner and minimization of L_(K+1)(x,y,z) to obtain a         new position estimation (x_(m),y_(m),z_(m)) for the transmitter         and possible loopback to the 5 preceding step.

The noise vector w_(K) has covariance matrix R=E[w_(K)w_(K) ^(H)]. By assuming that this matrix R is known, the criterion can be envisaged with a whitening technique.

Under these conditions we obtain the following criterion L_(K)′(x,y,z): $\begin{matrix} {{{L_{K}^{\prime}\left( {x,y,z} \right)} = \frac{{{c_{K}^{H}R^{- 1}{v_{K,c}\left( {x,y,z} \right)}}}^{2}}{\left( {c_{K}^{H}R^{- 1}c_{K}} \right)\left( {{v_{K,c}\left( {x,y,z} \right)}^{H}R^{- 1}{v_{K,c}\left( {x,y,z} \right)}} \right)}}{{{with}\quad R} = {E\left\lbrack {w_{K}w_{K}^{H}} \right\rbrack}}} & (12) \end{matrix}$

Other Variant of Implementation of the Method

According to another variant embodiment, the method constructs a vector Ĉ_(km) of dimension N×1 on the basis of the direction vector â_(km). For this purpose, the method applies a transformation which consists, for example, in choosing a reference instant k=i and in forming the ratios of the components of the vector â_(km) with the component corresponding to the instant i. The vector Ĉ′_(km) is then expressed in the following manner: $\begin{matrix} {{\hat{c}}_{k\quad m}^{\prime} = \begin{bmatrix} {{{\hat{a}}_{k\quad m}(1)}/{{\hat{a}}_{i\quad m}(1)}} \\ M \\ {{{\hat{a}}_{k\quad m}(n)}/{{\hat{a}}_{i\quad m}(n)}} \\ M \\ {{{\hat{a}}_{k\quad m}(N)}/{{\hat{a}}_{i\quad m}(N)}} \end{bmatrix}} & (13) \end{matrix}$ This corresponds to a temporal tracking of the measurements of the vector â_(k). Thus in a low noise context ||e_(km)||<<1, the components Ĉ′_(km) (n) of Ĉ′_(km) have expressions: $\begin{matrix} {{{{\hat{c}}_{k\quad m}^{\prime}(n)} \approx {\frac{v_{n}\left( {\theta_{k},\Delta_{k}} \right)}{v_{n}\left( {\theta_{i},\Delta_{i}} \right)} + {{\overset{\approx}{w}}_{k\quad m}(n)}}}{{{with}\text{:}\quad{{\overset{\approx}{w}}_{k\quad m}(n)}} = \frac{{{v_{n}\left( {\theta_{i},\Delta_{i}} \right)}{e_{k\quad m}(n)}} - {{v_{n}\left( {\theta_{k},\Delta_{k}} \right)}{e_{i\quad m}(n)}}}{\left( {v_{n}\left( {\theta_{i},\Delta_{i}} \right)} \right)^{2}}}} & (14) \end{matrix}$ Under these conditions the vector Ĉ′_(km) may be written in the following manner: $\begin{matrix} {{{\hat{c}}_{k\quad m}^{\prime} \approx {{c^{\prime}\left( {t_{k},x_{m},y_{m},z_{m}} \right)} + {\overset{\approx}{w}}_{k\quad m}}}{{{where}\quad{c^{\prime}\left( {t_{k},x_{m},y_{m},z_{m}} \right)}} = \begin{bmatrix} {{v_{1}\left( {\theta_{k},\Delta_{k}} \right)}/{v_{1}\left( {\theta_{i},\Delta_{i}} \right)}} \\ M \\ {{v_{N}\left( {\theta_{k},\Delta_{k}} \right)}/{v_{N}\left( {\theta_{i},\Delta_{i}} \right)}} \end{bmatrix}}{{and}\quad{{\overset{\approx}{w}}_{k\quad m}(n)}\quad{is}\quad{the}\quad n^{th}\quad{component}\quad{of}\quad{\overset{\sim}{w}}_{k\quad m}}} & {I(15)} \end{matrix}$ In the case of large running between the measurements, the method can determine vectors ĉ_(km) or Ĉ′_(km) constructed over a sliding time window (rather than over a constant window defined by a reference instant as is the case in the first variant) by taking i=k−1 or i=k−L, where L corresponds to the length of the window (number of measurement samples considered)

The measurement of the direction vectors â_(km) is generally obtained to within an undetermined complex factor. For the variant of the method using the vectors Ĉ′_(km), the method can comprise a step which consists in changing the phase reference of the direction vector measured by choosing a virtual channel as reference (and not a real channel as is the case in the first variant) defined, for example, by the phase barycenter (defined to within a constant scalar coefficient that may arbitrarily be fixed at 1). This operation is carried out, for example, by applying to the measured vectors â_(km) the following transformation: $\begin{matrix} {{\hat{a}}_{k\quad m}^{\prime} = {\left( {\prod\limits_{i}\frac{{\hat{a}}_{k\quad m}(i)}{){{a_{k\quad m}(i)}}}} \right)^{- \frac{1}{N}}{\hat{a}}_{k\quad m}}} & (16) \end{matrix}$ The correction coefficient is not fully determined by this expression having regard to the indeterminacy of order N at each instant k of the complex root. A tracking of the phase evolution during the observation period makes it possible to resolve the indeterminacy, as is described hereafter.

The complex correction coefficient being defined to within a factor from among the N N^(th) roots of unity, the phase tracking consists in arbitrarily fixing the first (k=1) correction coefficient (by taking root 1 for example), then in determining at each new iteration k+1, the correction coefficient ρ, from among the N^(th) roots of unity, which minimizes the mean phase deviations between the direction vector â_((k+1)m) measured at the instant k+1 and the corrected vector at the instant k â′_(km).

The minimization criterion, for measurements at the same frequency, can be defined by the following expression: $\begin{matrix} {\min\limits_{\rho \in \sqrt[N]{1}}{\sum\limits_{i \in {chanel}}{\min\begin{pmatrix} {\left. {{mod}\left( {{{\arg\left( \frac{\rho \cdot {{\hat{a}}_{{k + 1},m}(i)}}{{\hat{a}}_{k\quad m}^{\prime}(i)} \right.},{2\quad\pi}}} \right.} \right),} \\ {{2\quad\pi} - {{mod}\left( \left. {{\arg\left( \frac{\rho \cdot {{\hat{a}}_{{k + 1},m}(i)}}{{\hat{a}}_{k\quad m}^{\prime}(i)} \right.},{2\quad\pi}} \right) \right.}} \end{pmatrix}}}} & (17) \end{matrix}$

For measurements at different frequencies, it is possible to compare the phases of the components of the two direction vectors by correcting them for a power given by the ratio of these two frequencies.

If we consider the vectors Ĉ′_(km), it is then possible to compare them with the theoretical values c′(t_(k),x_(m),y_(m),z_(m)) for which the theoretical direction vector a(t_(k),x_(m),y_(m),z_(m)) is calculated with reference to the virtual channel defined by the phase barycenter (theoretical geometric phase barycenter which is the geometric locus for which the theoretical sum of the phase differences vanishes). This locus does not coincide, in general, with the phase center of the array (determined experimentally).

Locating the Transmitter On the Basis of the Ĉ′_(km)

The locating method thereafter comprises a step which consists in maximizing the following normalized vector correlation criterion L_(K)(x,y,z) in the position space (x,y,z) of a transmitter. $\begin{matrix} {{{L_{K}\left( {x,y,z} \right)} = \frac{{{c_{K}^{\prime\quad H}{v_{K,c^{\prime}}\left( {x,y,z} \right)}}}^{2}}{\left( {c_{K}^{\prime\quad H}c_{K}^{\prime}} \right)\left( {{v_{K,c^{\prime}}\left( {x,y,z} \right)}^{H}{v_{K,c^{\prime}}\left( {x,y,z} \right)}} \right)}}\begin{matrix} {{{with}\quad c_{K}^{\prime}} = \begin{bmatrix} c_{1\quad m}^{\prime} \\ M \\ c_{K\quad m}^{\prime} \end{bmatrix}} \\ {{= {{v_{K,c^{\prime}}\left( {x_{m},y_{m},z_{m}} \right)} + w_{K}}},{v_{K,c^{\prime}}\left( {x,y,z} \right)}} \\ {= \begin{bmatrix} {c^{\prime}\left( {t_{1},x,y,z} \right)} \\ M \\ {c^{\prime}\left( {t_{K},x,y,z} \right)} \end{bmatrix}} \end{matrix}{{{and}\quad w_{K}} = \begin{bmatrix} {\overset{\approx}{w}}_{1\quad m} \\ M \\ {\overset{\approx}{w}}_{K\quad m} \end{bmatrix}}} & (18) \end{matrix}$

To obtain the position (x_(m),y_(m),z_(m)) of the transmitter, the method calculates and maximizes the criterion L_(K)(x,y,z) of equation (18).

In order to refine the estimation of the position (x_(m),y_(m),y_(m)) of the transmitters the steps of the method can be conducted in an iterative manner, for example in the following manner:

-   -   Step I3 Identification of the vectors c′_((K+1)m) at the instant         t_(K+1).     -   Step I4 Calculation of the criterion L_(K+1)(x,y,z) in an         iterative manner and minimization of L_(K+1)(x,y,z) to obtain a         new position estimation (x_(m),y_(m),z_(m)) for the transmitter.

The noise vector w_(K) has covariance matrix R=E[w_(K)w_(K) ^(H)]. For a known matrix R, the criterion can be envisaged with a whitening technique. Under these conditions we obtain the following criterion L_(K)′(x,y,z): $\begin{matrix} {{{L_{K^{\prime}}\left( {x,y,z} \right)}\quad = \quad\frac{{{c_{K}^{\prime\quad H}\quad R^{- 1}\quad{v_{K,\quad c^{\prime}}\left( {x,y,z} \right)}}}^{2}}{\left( {c_{K}^{\prime\quad H}\quad R^{- 1}\quad c_{K}^{\prime}} \right)\quad\left( {{v_{K,\quad c^{\prime}}\left( {x,y,z} \right)}^{H}\quad R^{- 1}\quad{v_{K,\quad c^{\prime}}\left( {x,y,z} \right)}} \right)}}{{{with}\quad R} = {E\left\lbrack {w_{K}\quad w_{K}^{H}} \right\rbrack}}} & (19) \end{matrix}$

Filtering Step

In the case of a very large number of measurements, the method can for example comprise a step of prior processing of the vectors a_(k) at the K instants t_(k). This processing, executed before the steps for determining the coefficients Ĉ_(km) or Ĉ_(km), makes it possible to reduce the numerical complexity of calculation (which is dependent on the number of measurements) by decreasing K. By way of example, it is possible to perform on the elementary measurements the following processings:

-   -   decimation of the instants t_(k),     -   filtering (smoothing of the measurements â_(km)) and under         sampling,     -   merging of the measurements over a defined duration (extraction         by association of direction vector and production of synthesis         measurements).

In the variant of the method using the vectors Ĉ′_(km), it is possible to introduce a model on the variation in level of the received signal based, for example, on a free-space propagation model.

The method in its general form, by recourse to the criteria of vector correlation between measurements and models (L_(K)(x,y,z) and L_(K)′(x,y,z)), can take into account other observation models derived from the direction vectors a_(k).

In the presence of an array of paired antennas, it is notably possible to define an observation model combining the vectors b_(k) and C_(K). or c′_(km).

According to a variant embodiment, it is possible to use the filtering method described in patent application FR 03/13128. If the decimation ratio is significant (non-negligible transit between two filtered measurements), it is also possible to supplement the decimation with an estimation of the variation in direction vector, and more particularly the rate of variation of the differential phase for each of the channels, and to employ a distance-based model utilizing this variation.

Specifically, the phase of each component b_(k,n) of the relative vector b_(k) is dependent on the incidence (θ_(k),Δ_(k)) and on the angle α_(n) formed by the axis defined by the positions of the aerials of the channels n and 1 with the trajectory of the carrier.

If γ is the angle formed by the direction of incidence and the trajectory of the carrier (pseudo bearing), we have: $b_{k,n} = {{\rho_{k,n}{\mathbb{e}}^{{j \cdot \Delta}\quad{\varphi_{n}{(t)}}}\quad{with}\text{:}\quad\Delta\quad{\varphi_{n}(t)}} = {2\quad p\quad\frac{d}{\lambda_{0}(t)}{\cos\left( {{\gamma(t)} + \alpha_{n}} \right)}}}$ The instantaneous variation of differential phase may then be written: ${\Delta{\overset{.}{\varphi}(t)}} = {\frac{V}{D} \cdot {\sin\left( \theta_{k} \right)} \cdot {{tg}\left( {\theta_{k} + \alpha_{n}} \right)} \cdot {{\Delta\varphi}(t)}}$ from which we derive a relation on the distance of the transmitter: $\begin{matrix} {{D(t)} = {\frac{V}{\Delta\quad{\overset{.}{\varphi}(t)}} \cdot {\sin\left( \theta_{k} \right)} \cdot {{tg}\left( {\theta_{k} + \alpha_{n}} \right)} \cdot {{\Delta\varphi}(t)}}} & (20) \end{matrix}$ This relation then makes it possible, as an adjunct to the vectors b_(k) or c_(k), to employ the estimations of instantaneous variation of differential phase by introducing a distance model into the correlation criterion L_(K)(x,y,z). In the case where γ=0 (aerials along the axis of the carrier), the relations may be written: $\frac{b_{k,n}}{b_{k,n}} = {\exp\left( {{j2\pi}\quad\frac{d}{\lambda}{\cos\left( {\theta\left( {t_{k},x_{m},y_{m},z_{m}} \right)} \right)}{\cos\left( {\Delta\left( {t_{k},x_{m},y_{m},z_{m}} \right)} \right)}} \right)}$ ${D(t)} = {\left( {{\cos(\theta)} - \frac{1}{\cos(\theta)}} \right)\frac{V}{\Delta\quad{\overset{.}{\varphi}(t)}}\Delta\quad{\varphi(t)}}$ 

1. A method of locating one or more transmitters on the basis of an array of sensors moving with respect to the transmitters the method of comprising the following steps: determining Direction vectors â_(k) corresponding to a response of the array of sensors to a source with incidence (θ, Δ) as a function of incidence parameters θ, Δ, and of parameter ρ related to the distortion of the phases on the sensors, transforming the vector â_(k) so as to eliminate the unknown parameter ρ, into a transformed vector ĉ_(km), ĉ′_(km), and using the transformed vector to obtain the position of the transmitter using a maximized locating criterion.
 2. The method as claimed in claim 1, wherein the transformation step comprises the following steps: choosing a reference channel or sensor and constructing a vector b(t_(k),x_(m),y_(m),z_(m), ρ) whose components correspond to the ratio of 2 channels, $\begin{bmatrix} {\left( {\rho_{2}{v_{2}\left( {\theta_{k},\Delta_{k}} \right)}} \right)/\left( {\rho_{1}{v_{1}\left( {\theta_{k},\Delta_{k}} \right)}} \right)} \\ M \\ {\left( {\rho_{N}{v_{N}\left( {\theta_{k},\Delta_{k}} \right)}} \right)/\left( {\rho_{1}{v_{1}\left( {\theta_{k},\Delta_{k}} \right)}} \right)} \end{bmatrix}\quad$ o choosing a reference instant and constructing on the basis of the vector b(t_(k),x_(m),y_(m),z_(m),ρ) a vector whose components are: ${\hat{c}}_{k\quad m} = \begin{bmatrix} {{{\hat{b}}_{k\quad m}(1)}/{{\hat{b}}_{im}(1)}} \\ M \\ {{{\hat{b}}_{k\quad m}(n)}/{{\hat{b}}_{im}(n)}} \\ M \\ {{{\hat{b}}_{k\quad m}\left( {N - 1} \right)}/{{\hat{b}}_{im}\left( {N - 1} \right)}} \end{bmatrix}$
 3. The method as claimed in claim 2, wherein the locating criterion is a normalized vector correlation criterion L_(k)(x, y, z) in the position space (x, y, z) of a transmitter with: ${L_{K}\left( {x,y,z} \right)} = \frac{{{c_{K}^{H}{v_{K,c}\left( {x,y,z} \right)}}}^{2}}{\left( {c_{K}^{H}c_{K}} \right)\left( {{v_{K,c}\left( {x,y,z} \right)}^{H}{v_{K,c}\left( {x,y,z} \right)}} \right)}$ with ${c_{K} = {\begin{bmatrix} c_{1m} \\ M \\ c_{Km} \end{bmatrix} = {{v_{K,c}\left( {x_{m},y_{m},z_{m}} \right)} + w_{K}}}},{{v_{K,c}\left( {x,y,z} \right)} = \begin{bmatrix} {c\left( {t_{1},x,y,z} \right)} \\ M \\ {c\left( {t_{K},x,y,z} \right)} \end{bmatrix}}$ and $w_{K} = \begin{bmatrix} {\overset{\sim}{w}}_{1m} \\ M \\ {\overset{\sim}{w}}_{Km} \end{bmatrix}$ noise vector for all the positions of the transmitter
 4. The method as claimed in one of claim 3, wherein it comprises the following iterative steps: identifying the vectors c_((K+1)m) at the instant t_(k+1). calculating the criterion L_(K+1)(x,y,z) in an iterative manner and minimizing L_(K+1)(x,y,z) to obtain a new position estimation (x_(m),y_(m),z_(m)) for the transmitter and possible loopback to the preceding step I1.
 5. The method as claimed in claim 1, wherein the transformation step comprises the following steps: choosing a reference instant i, and constructing a vector Ĉ′_(km) whose components correspond to the ratio of the components between the given instant k and the instant i. ${\hat{c}}_{k\quad m}^{\prime} = \begin{bmatrix} {{{\hat{a}}_{k\quad m}(1)}/{{\hat{a}}_{im}(1)}} \\ M \\ {{{\hat{a}}_{k\quad m}(n)}/{{\hat{a}}_{im}(n)}} \\ M \\ {{{\hat{a}}_{k\quad m}(N)}/{{\hat{a}}_{im}(N)}} \end{bmatrix}$
 6. The method as claimed in claim 5, wherein the locating criterion is equal to: ${L_{K}\left( {x,y,z} \right)} = \frac{{{c_{K}^{\prime\quad H}{v_{K,c^{\prime}}\left( {x,y,z} \right)}}}^{2}}{\left( {c_{K}^{\prime\quad H}c_{K}^{\prime}} \right)\left( {{v_{K,c^{\prime}}\left( {x,y,z} \right)}^{H}{v_{K,c^{\prime}}\left( {x,y,z} \right)}} \right)}$ with ${c_{K}^{\prime} = {\begin{bmatrix} c_{1m}^{\prime} \\ M \\ c_{Km}^{\prime} \end{bmatrix} = {{v_{K,c^{\prime}}\left( {x_{m},y_{m},z_{m}} \right)} + w_{K}}}},{{v_{K,c^{\prime}}\left( {x,y,z} \right)} = \begin{bmatrix} {c^{\prime}\left( {t_{1},x,y,z} \right)} \\ M \\ {c^{\prime}\left( {t_{K},x,y,z} \right)} \end{bmatrix}}$ and $w_{K} = \begin{bmatrix} {\overset{\approx}{w}}_{1m} \\ M \\ {\overset{\approx}{w}}_{Km} \end{bmatrix}$ noise vector for all the components
 7. The method as claimed in claim 5, wherein it comprises the following iterative steps: identification of the vectors c′_((K+1)m) at the instant t_(K+1). calculation of the criterion L_(K+1)(x,y,z) in an iterative manner and minimization of L_(K+1)(x,y,z) to obtain a new position estimation (x_(m),y_(m),z_(m)) for the transmitter.
 8. The method as claimed in claim 5, wherein a phase tracking is performed for the vectors ĉ′_(km).
 9. The method as claimed in claim 1, wherein it comprises a step of filtering the direction vectors â_(k).
 10. The method as claimed in claim 1, wherein a sliding time window is used by taking i=k−1 or i=k−L.
 11. The method as claimed in claim 6, wherein it comprises the following iterative steps: identification of the vectors c′_(K+1)m) at the instant t_(K+1). calculation of the criterion L_(K+1)(x,y,z) in an iterative manner and minimization of L_(K+1)(x,y,z) to obtain a new position estimation (x_(m),y_(m),z_(m)) for the transmitter. 